FEATURES CONNECTION DIAGRAM AD8422 -IN 1 RG 2 RG 3 6 REF +IN 4 5 -VS 8 +VS 7 VOUT TOP VIEW (Not to Scale) Figure 1. 8-Lead MSOP (RM), 8-Lead SOIC (R) -20 RL = 2k VOUT = 10V -30 -40 -50 AMPLITUDE (dBc) Low power: 330 A maximum quiescent current Rail-to-rail output Low noise and distortion 8 nV/Hz maximum input voltage noise at 1 kHz 0.15 V p-p RTI noise (G = 100) 0.5 ppm nonlinearity with 2 k load (G = 1) Excellent ac specifications 80 dB minimum CMRR at 10 kHz (G = 1) 2.2 MHz bandwidth (G = 1) High precision dc performance (AD8422BRZ) 150 dB minimum CMRR (G = 1000) 0.04% maximum gain error (G = 1000) 0.3 V/C maximum input offset drift 0.5 nA maximum input bias current Wide supply range 4.6 V to 36 V single supply 2.3 V to 18 V dual supply Input overvoltage protection: 40 V from opposite supply Gain range: 1 to 1000 11197-001 -60 -70 -80 G = 1000 -90 -100 G = 100 -110 G = 10 G=1 -120 -130 APPLICATIONS -140 10 Medical instrumentation Industrial process controls Strain gages Transducer interfaces Precision data acquisition systems Channel-isolated systems Portable instrumentation 100 FREQUENCY (Hz) 1k 5k 11197-102 Data Sheet High Performance, Low Power, Rail-to-Rail Precision Instrumentation Amplifier AD8422 Figure 2. Total Harmonic Distortion vs. Frequency GENERAL DESCRIPTION The AD8422 is a high precision, low power, low noise, rail-to-rail instrumentation amplifier that delivers the best performance per unit microampere in the industry. The AD8422 processes signals with ultralow distortion performance that is load independent over its full output range. The AD8422 is the third generation development of the industrystandard AD620. The AD8422 employs new process technologies and design techniques to achieve higher dynamic range and lower errors than its predecessors, while consuming less than one-third of the power. The AD8422 uses the high performance pinout introduced by the AD8221. Very low bias current makes the AD8422 error-free with high source impedance, allowing multiple sensors to be multiplexed to the inputs. Low voltage noise and low current noise make the AD8422 an ideal choice for measuring a Wheatstone bridge. Rev. A The wide input range and rail-to-rail output of the AD8422 bring all of the benefits of a high performance in-amp to singlesupply applications. Whether using high or low supply voltages, the power savings make the AD8422 an excellent choice for high channel count or power sensitive applications on a very tight error budget. The AD8422 uses robust input protection that ensures reliability without sacrificing noise performance. The AD8422 has high ESD immunity, and the inputs are protected from continuous voltages up to 40 V from the opposite supply rail. A single resistor sets the gain from 1 to 1000. The reference pin can be used to apply a precise offset to the output voltage. The AD8422 is specified from -40C to +85C and has typical performance curves to 125C. It is available in 8-lead MSOP and 8-lead SOIC packages. Document Feedback Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. Specifications subject to change without notice. No license is granted by implication or otherwise under any patent or patent rights of Analog Devices. Trademarks and registered trademarks are the property of their respective owners. One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A. Tel: 781.329.4700 (c)2013-2015 Analog Devices, Inc. All rights reserved. Technical Support www.analog.com AD8422 Data Sheet TABLE OF CONTENTS Features .............................................................................................. 1 Architecture ................................................................................ 19 Applications ....................................................................................... 1 Gain Selection ............................................................................. 19 Connection Diagram ....................................................................... 1 Reference Terminal .................................................................... 20 General Description ......................................................................... 1 Input Voltage Range ................................................................... 20 Revision History ............................................................................... 2 Layout .......................................................................................... 20 Specifications..................................................................................... 3 Input Bias Current Return Path ............................................... 21 SOIC Package ................................................................................ 3 Input Voltages Beyond the Supply Rails.................................. 21 MSOP Package .............................................................................. 5 Radio Frequency Interference (RFI) ........................................ 22 Absolute Maximum Ratings............................................................ 8 Applications Information .............................................................. 23 Thermal Resistance ...................................................................... 8 Precision Bridge Conditioning ................................................. 23 ESD Caution .................................................................................. 8 Process Control Analog Input .................................................. 23 Pin Configuration and Function Descriptions ............................. 9 Outline Dimensions ....................................................................... 24 Typical Performance Characteristics ........................................... 10 Ordering Guide .......................................................................... 24 Theory of Operation ...................................................................... 19 REVISION HISTORY 1/15--Rev. 0 to Rev. A Changes to Features Section............................................................ 1 Changes to SOIC Package Section and Table 1 ............................ 4 Changes to MSOP Package Section and Table 2 .......................... 5 Changes to Supply Voltage Parameter and ESD Parameter, Table 3 .................................................................... 8 Deleted Figure 12 and Figure 15, Renumbered Sequentially ... 11 Changes to Figure 10 to Figure 15 ................................................ 11 Changes to Figure 16, Figure 18, and Figure 19 ......................... 12 Changes to Figure 23 and Figure 24 ............................................. 13 Changes to Figure 31, Figure 32, and Figure 33 ......................... 14 Changes to Figure 64 ...................................................................... 23 5/13--Revision 0: Initial Version Rev. A | Page 2 of 24 Data Sheet AD8422 SPECIFICATIONS SOIC PACKAGE VS = 15 V, VREF = 0 V, V+IN = 0 V, V-IN = 0 V, TA = 25C, G = 1, RL = 2 k, unless otherwise noted. Table 1. Parameter COMMON-MODE REJECTION RATIO CMRR DC to 60 Hz with 1 k Source Imbalance G=1 G = 10 G = 100 G = 1000 Over Temperature, G=1 CMRR at 10 kHz G=1 G = 10 G = 100 G = 1000 NOISE1 Voltage Noise, 1 kHz Input Voltage Noise, eNI Output Voltage Noise, eNO Peak to Peak, RTI G=1 G = 10 G = 100 to 1000 Current Noise VOLTAGE OFFSET2 Input Offset, VOSI Over Temperature Average Temperature Coefficient Output Offset, VOSO Over Temperature Average Temperature Coefficient Offset RTI vs. Supply (PSR) G=1 G = 10 G = 100 G = 1000 INPUT CURRENT Input Bias Current Over Temperature Average Temperature Coefficient Input Offset Current Over Temperature Average Temperature Coefficient Test Conditions/ Comments Min AD8422ARZ Typ Max Min AD8422BRZ Typ Max Unit VCM = -10 V to +10 V T = -40C to +85C VCM = -10 V to +10 V 86 106 126 146 83 94 114 134 150 89 dB dB dB dB dB 80 90 100 100 80 95 100 100 dB dB dB dB VIN+, VIN-, VREF = 0 V 8 80 8 80 nV/Hz nV/Hz f = 0.1 Hz to 10 Hz 2 0.5 0.15 90 8 f = 1 kHz f = 0.1 Hz to 10 Hz 2 0.5 0.15 90 8 110 V p-p V p-p V p-p fA/Hz pA p-p VS = 2.3 V to 15 V T = -40C to +85C 60 70 0.4 25 40 0.3 V V V/C VS = 2.3 V to 15 V T = -40C to +85C 300 500 5 150 300 2 V V V/C VS = 2.3 V to 18 V 90 110 124 130 VS = 2.3 V to 15 V T = -40C to +85C 110 130 150 150 0.5 100 120 140 140 1 2 4 VS = 2.3 V to 15 V T = -40C to +85C 0.2 1 Rev. A | Page 3 of 24 120 140 160 160 0.2 dB dB dB dB 0.5 1 nA nA pA/C 0.15 0.3 nA nA pA/C 4 0.3 0.8 0.1 1 AD8422 Parameter REFERENCE INPUT RIN IIN Voltage Range Gain to Output DYNAMIC RESPONSE Small Signal -3 dB Bandwidth G=1 G = 10 G = 100 G = 1000 Settling Time 0.01% G=1 G = 10 G = 100 G = 1000 Settling Time 0.001% G=1 G = 10 G = 100 G = 1000 Slew Rate GAIN3 Gain Range Gain Error G=1 G = 10 G = 100 G = 1000 Gain Nonlinearity G=1 G = 10 G = 100 G = 1000 Gain vs. Temperature G=1 G>1 INPUT Input Impedance Differential Common Mode Input Operating Voltage Range4 Over Temperature OUTPUT Output Swing, RL = 10 k Over Temperature Output Swing, RL = 10 k Over Temperature Output Swing, RL = 2 k Over Temperature5 Output Swing, RL = 2 k Over Temperature Short-Circuit Current Data Sheet Test Conditions/ Comments Min AD8422ARZ Typ Max 20 35 VIN+, VIN-, VREF = 0 V Min AD8422BRZ Typ Max 1 1 k A V V/V 2200 850 120 12 2200 850 120 12 kHz kHz kHz kHz 13 13 12 80 13 13 12 80 s s s s 15 15 15 160 15 15 15 160 s s s s V/s -VS 50 +VS 20 35 Unit -VS 50 +VS 10 V step 10 V step G = 1 to 100 G = 1 + (19.8 k/RG) 0.8 0.8 1 1000 1 1000 V/V 0.01 0.04 0.04 0.04 % % % % 5 5 10 20 ppm ppm ppm ppm 1 -80 ppm/C ppm/C G||pF G||pF V V VOUT 10 V 0.03 0.2 0.2 0.2 VOUT = -10 V to +10 V RL = 2 k 0.5 2 4 10 5 5 10 20 0.5 2 4 10 5 -80 200||2 200||2 200||2 200||2 VS = 2.3 V to 18 V T = -40C to +85C -VS + 1.2 -VS + 1.2 +VS - 1.2 +VS - 1.3 -VS + 1.2 -VS + 1.2 +VS - 1.2 +VS - 1.3 VS = 15 V T = -40C to +85C VS = 2.3 V T = -40C to +85C VS = 15 V T = -40C to +85C VS = 2.3 V T = -40C to +85C -VS + 0.2 -VS + 0.25 -VS + 0.12 -VS + 0.13 -VS + 0.25 -VS + 0.3 -VS + 0.16 -VS + 0.2 +VS - 0.2 +VS - 0.25 +VS - 0.12 +VS - 0.13 +VS - 0.25 +VS - 1.4 +VS - 0.16 +VS - 0.2 -VS + 0.2 -VS + 0.25 -VS + 0.12 -VS + 0.13 -VS + 0.25 -VS + 0.3 -VS + 0.16 -VS + 0.2 +VS - 0.2 +VS - 0.25 +VS - 0.12 +VS - 0.13 +VS - 0.25 +VS - 1.4 +VS - 0.16 +VS - 0.2 20 Rev. A | Page 4 of 24 20 V V V V V V V V mA Data Sheet Parameter POWER SUPPLY Operating Range Quiescent Current Over Temperature TEMPERATURE RANGE Specified Performance Operating Range6 AD8422 Test Conditions/ Comments Dual-supply operation Single-supply operation Min AD8422ARZ Typ Max Min AD8422BRZ Typ Max 2.3 4.6 18 36 2.3 4.6 18 36 V V 330 400 A A +85 +125 C C 300 T = -40C to +85C -40 -40 330 400 +85 +125 300 -40 -40 Unit Total RTI noise = eNI2 + (eNO/G)2 Total RTI VOS = (VOSI) + (VOSO/G). 3 Gain does not include the effects of the external resistor, RG. 4 One input grounded. G = 1. 5 Output current limited at cold temperatures. See Figure 33. 6 See Typical Performance Characteristics for expected operation between 85C and 125C. 1 2 MSOP PACKAGE VS = 15 V, VREF = 0 V, V+IN = 0 V, V-IN = 0 V, TA = 25C, G = 1, RL = 2 k, unless otherwise noted. Table 2. Parameter COMMON-MODE REJECTION RATIO CMRR DC to 60 Hz with 1 k Source Imbalance G=1 G = 10 G = 100 G = 1000 Over Temperature, G = 1 CMRR at 10 kHz G=1 G = 10 G = 100 G = 1000 NOISE1 Voltage Noise, 1 kHz Input Voltage Noise, eNI Output Voltage Noise, eNO Peak to Peak, RTI G=1 G = 10 G = 100 to 1000 Current Noise VOLTAGE OFFSET2 Input Offset, VOSI Over Temperature Average Temperature Coefficient Output Offset, VOSO Over Temperature Average Temperature Coefficient Test Conditions/ Comments Min AD8422ARMZ Typ Max Min AD8422BRMZ Typ Max Unit VCM = -10 V to +10 V T = -40C to +85C VCM = -10 V to +10 V 86 106 126 146 83 90 110 130 150 86 dB dB dB dB 80 90 100 100 80 95 100 100 dB dB dB dB VIN+, VIN-, VREF = 0 V 8 80 8 80 nV/Hz nV/Hz f = 0.1 Hz to 10 Hz f = 1 kHz f = 0.1 Hz to 10 Hz 2 0.5 0.15 90 8 2 0.5 0.15 90 8 110 V p-p V p-p V p-p fA/Hz pA p-p VS = 2.3 V to 15 V T = -40C to +85C 70 110 0.6 50 75 0.4 V V V/C VS = 2.3 V to 15 V T = -40C to +85C 300 500 5 150 300 2 V V V/C Rev. A | Page 5 of 24 AD8422 Parameter Offset RTI vs. Supply (PSR) G=1 G = 10 G = 100 G = 1000 INPUT CURRENT Input Bias Current Over Temperature Average Temperature Coefficient Input Offset Current Over Temperature Average Temperature Coefficient REFERENCE INPUT RIN IIN Voltage Range Gain to Output DYNAMIC RESPONSE Small Signal -3 dB Bandwidth G=1 G = 10 G = 100 G = 1000 Settling Time 0.01% G=1 G = 10 G = 100 G = 1000 Settling Time 0.001% G=1 G = 10 G = 100 G = 1000 Slew Rate GAIN3 Gain Range Gain Error G=1 G = 10 G = 100 G = 1000 Gain Nonlinearity G=1 G = 10 G = 100 G = 1000 Gain vs. Temperature G=1 G>1 Data Sheet Test Conditions/ Comments VS = 2.3 V to 18 V Min 90 110 124 130 VS = 2.3 V to 15 V T = -40C to +85C AD8422ARMZ Typ Max 110 130 150 150 0.5 Min 100 120 140 140 1 2 0.2 0.3 0.8 0.1 20 35 0.5 1 nA nA pA/C 0.15 0.3 nA nA pA/C 1 1 1 k A V V/V 2200 850 120 12 2200 850 120 12 kHz kHz kHz kHz 13 13 12 80 13 13 12 80 s s s s 15 15 15 160 15 15 15 160 s s s s V/s -VS 50 +VS 20 35 Unit dB dB dB dB 4 1 VIN+, VIN-, VREF = 0 V 120 140 160 160 0.2 4 VS = 2.3 V to 15 V T = -40C to +85C AD8422BRMZ Typ Max -VS 50 +VS 10 V step 10 V step G = 1 to 100 G = 1 + (19.8 k/RG) 0.8 0.8 1 1000 1 1000 V/V 0.01 0.04 0.04 0.04 % % % % 5 5 10 20 ppm ppm ppm ppm 1 -80 ppm/C ppm/C VOUT 10 V 0.03 0.2 0.2 0.2 VOUT = -10 V to +10 V RL = 2 k 0.5 2 4 10 5 5 10 20 5 -80 Rev. A | Page 6 of 24 0.5 2 4 10 Data Sheet Parameter INPUT Input Impedance Differential Common Mode Input Operating Voltage Range4 Over Temperature OUTPUT Output Swing, RL = 10 k Over Temperature Output Swing, RL = 10 k Over Temperature Output Swing, RL = 2 k Over Temperature5 Output Swing, RL = 2 k Over Temperature Short-Circuit Current POWER SUPPLY Operating Range Quiescent Current Over Temperature TEMPERATURE RANGE Specified Performance Operating Range6 AD8422 Test Conditions/ Comments Min AD8422ARMZ Typ Max Min 200||2 200||2 AD8422BRMZ Typ Max 200||2 200||2 Unit G||pF G||pF VS = 2.3 V to 18 V T = -40C to +85C -VS + 1.2 -VS + 1.2 +VS - 1.2 +VS - 1.3 -VS + 1.2 -VS + 1.2 +VS - 1.2 +VS - 1.3 V V VS = 15 V T = -40C to +85C VS = 2.3 V T = -40C to +85C VS = 15 V T = -40C to +85C VS = 2.3 V T = -40C to +85C -VS + 0.2 -VS + 0.25 -VS + 0.12 -VS + 0.13 -VS + 0.25 -VS + 0.3 -VS + 0.16 -VS + 0.2 +VS - 0.2 +VS - 0.25 +VS - 0.12 +VS - 0.13 +VS - 0.25 +VS - 1.4 +VS - 0.16 +VS - 0.2 -VS + 0.2 -VS + 0.25 -VS + 0.12 -VS + 0.13 -VS + 0.25 -VS + 0.3 -VS + 0.16 -VS + 0.2 +VS - 0.2 +VS - 0.25 +VS - 0.12 +VS - 0.13 +VS - 0.25 +VS - 1.4 +VS - 0.16 +VS - 0.2 V V V V V V V V mA 18 36 330 400 V V A A +85 +125 C C 20 Dual-supply operation Single-supply operation 2.3 4.6 300 T = -40C to +85C -40 -40 Total RTI Noise = eNI2 + (eNO/G)2 Total RTI VOS = (VOSI) + (VOSO/G). 3 Gain does not include the effects of the external resistor, RG. 4 One input grounded. G = 1. 5 Output current limited at cold temperatures. See Figure 33. 6 See Typical Performance Characteristics for expected operation between 85C and 125C. 1 2 Rev. A | Page 7 of 24 20 18 36 330 400 2.3 4.6 +85 +125 -40 -40 300 AD8422 Data Sheet ABSOLUTE MAXIMUM RATINGS THERMAL RESISTANCE Table 3. Parameter Supply Voltage Output Short-Circuit Current Duration Maximum Voltage at -IN or +IN1 Minimum Voltage at -IN or +IN Maximum Voltage at REF Storage Temperature Range Operating Temperature Range Maximum Junction Temperature ESD Human Body Model Charge Device Model Machine Model 1 JA is specified for a device in free air using a 4-layer JEDEC printed circuit board (PCB). Rating 2.3 V to 18 V Indefinite -VS + 40 V +VS - 40 V VS 0.3 V -65C to +150C -40C to +125C 150C Table 4. Package 8-Lead SOIC 8-Lead MSOP ESD CAUTION 2.5 kV 1.25 kV 100 V For voltages beyond these limits, use input protection resistors. See the Theory of Operation section for more information. Stresses at or above those listed under Absolute Maximum Ratings may cause permanent damage to the product. This is a stress rating only; functional operation of the product at these or any other conditions above those indicated in the operational section of this specification is not implied. Operation beyond the maximum operating conditions for extended periods may affect product reliability. Rev. A | Page 8 of 24 JA 100 162 Unit C/W C/W Data Sheet AD8422 AD8422 8 +VS 2 7 VOUT RG 3 6 REF +IN 4 5 -VS -IN 1 RG TOP VIEW (Not to Scale) 11197-002 PIN CONFIGURATION AND FUNCTION DESCRIPTIONS Figure 3. Pin Configuration Table 5. Pin Function Descriptions Pin No. 1 2, 3 4 5 6 7 8 Mnemonic -IN RG +IN -VS REF VOUT +VS Description Negative Input Terminal. Gain Setting Terminals. Place resistor across the RG pins to set the gain. G = 1 + (19.8 k/RG). Positive Input Terminal. Negative Power Supply Terminal. Reference Voltage Terminal. Drive this terminal with a low impedance voltage source to level shift the output. Output Terminal. Positive Power Supply Terminal. Rev. A | Page 9 of 24 AD8422 Data Sheet TYPICAL PERFORMANCE CHARACTERISTICS T = 25C, VS = 15, VREF = 0 V, RL = 10 k, unless otherwise noted. 400 400 350 350 300 250 200 200 150 150 100 100 50 50 0 -90 -60 -30 0 30 INPUT OFFSET VOLTAGE (V) 60 90 0 -300 -200 -100 0 100 200 300 OUTPUT OFFSET VOLTAGE (V) Figure 4. Typical Distribution of Input Offset Voltage 11197-006 HITS 250 11197-003 Figure 7. Typical Distribution of Output Offset Voltage 800 400 600 HITS HITS 300 400 200 200 100 -600 -300 0 300 600 POSITIVE INPUT BIAS CURRENT (pA) 900 0 -300 11197-004 0 -900 -200 -100 0 100 200 300 INPUT OFFSET CURRENT (pA) 11197-007 HITS 300 Figure 8. Typical Distribution of Input Offset Current Figure 5. Typical Distribution of Input Bias Current 500 500 400 HITS 300 200 100 100 -6 -3 3 0 PSRR G = 1 (V/V) 6 9 0 -40 -20 0 CMRR G = 1 (V/V) 20 Figure 9. Typical Distribution of CMRR (G = 1) Figure 6. Typical Distribution of PSRR (G = 1) Rev. A | Page 10 of 24 40 11197-008 0 -9 300 200 11197-005 HITS 400 Data Sheet AD8422 5.0 20 G = 100 VS = 15V 10 VS = 12V 0 VS = 5V -10 -15 2.5 2.0 1.5 1.0 VREF = 0V 0.5 -10 -5 0 5 10 15 20 OUTPUT VOLTAGE (V) 0 -0.5 0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 Figure 13. Input Common-Mode Voltage vs. Output Voltage (G = 100), Single-Supply, VS = 5 V 5.0 20 5.0 G=1 4.5 VS = 5V G=1 VREF = 2.5V VIN- = 2.5V 4.5 VREF = 0V VREF = 2.5V 4.0 OUTPUT VOLTAGE (V) 3.5 3.0 2.5 2.0 1.5 16 VOUT 12 IIN 3.5 8 3.0 4 2.5 0 2.0 -4 1.5 -8 1.0 -12 0.5 -16 1.0 0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 5.5 OUTPUT VOLTAGE (V) 11197-010 0.5 0 -0.5 0 -35 -30 -25 -20 -15 -10 -5 10 15 20 25 30 35 40 20 G = 100 VS = 15V 20 VS = 15V G=1 VREF = 0V VIN- = 0V 15 10 15 10 0 -5 VS = 5V -10 -15 -15 -10 -5 0 5 OUTPUT VOLTAGE (V) 10 15 20 10 VOUT OUTPUT VOLTAGE (V) VS = 12V 5 11197-012 INPUT COMMON-MODE VOLTAGE (V) 5 Figure 14. Input Overvoltage Performance; G = 1, VS = 5 V 20 -20 -20 -20 0 INPUT VOLTAGE (V) Figure 11. Input Common-Mode Voltage vs. Output Voltage (G = 1), Single-Supply, VS = 5 V 15 5.5 5.0 OUTPUT VOLTAGE (V) Figure 10. Input Common-Mode Voltage vs. Output Voltage (G = 1), VS = 15 V, VS = 12 V, VS = 5 V 4.0 0 INPUT CURRENT (mA) -15 VREF = 2.5V 11197-015 -20 -20 INPUT COMMON-MODE VOLTAGE (V) 3.0 5 5 IIN 0 0 -5 -5 -10 -10 -15 -15 -20 -25 Figure 12. Input Common-Mode Voltage vs. Output Voltage (G = 100), VS = 15 V, VS = 12 V, VS = 5 V Rev. A | Page 11 of 24 -20 -20 -15 -10 0 5 10 -5 INPUT VOLTAGE (V) 15 20 25 Figure 15. Input Overvoltage Performance; G = 1, VS = 15 V INPUT CURRENT (mA) -5 3.5 11197-016 5 4.0 11197-013 INPUT COMMON-MODE VOLTAGE (V) 4.5 15 11197-009 INPUT COMMON-MODE VOLTAGE (V) G=1 AD8422 Data Sheet 0.15 VOUT INPUT BIAS CURRENT (nA) 12 8 3.0 4 2.5 0 2.0 -4 1.5 -8 1.0 -12 0.5 -16 0 -35 -30 -25 -20 -15 -10 -5 INPUT CURRENT (mA) IIN 3.5 -20 0 5 10 15 20 25 30 35 40 INPUT VOLTAGE (V) 3.5 4.0 -5 -5 -10 -10 -15 -15 15 20 80 60 40 0 0.1 11197-018 0 5 10 -5 INPUT VOLTAGE (V) GAIN = 1 100 20 -20 -10 GAIN = 10 120 25 1 10 100 1k FREQUENCY (Hz) 10k 100k 11197-021 0 POSITIVE PSRR (dB) 5 INPUT CURRENT (mA) IIN 10k 100k Figure 20. Positive PSRR vs. Frequency Figure 17. Input Overvoltage Performance; G = 100, VS = 15 V 180 0.25 VS = 15V 0.20 160 0.15 140 GAIN = 1000 NEGATIVE PSRR (dB) GAIN = 100 0.10 0.05 0 -0.05 -0.10 GAIN = 10 120 GAIN = 1 100 80 60 40 -0.15 20 -0.20 -10 -5 0 5 COMMON-MODE VOLTAGE (V) 10 15 11197-019 OUTPUT VOLTAGE (V) 3.0 GAIN = 100 140 0 INPUT BIAS CURRENT (nA) 2.5 GAIN = 1000 15 5 -0.25 -15 2.0 180 10 -15 1.5 Figure 19. Input Bias Current vs. Common-Mode Voltage, VS = 5 V VOUT -20 -0.10 160 10 -20 -25 -0.05 11197-022 15 0 COMMON-MODE VOLTAGE (V) 20 VS = 15V G = 100 VREF = 0V VIN- = 0V 0.05 -0.20 1.0 Figure 16. Input Overvoltage Performance; G = 100, VS = 5 V 20 0.10 -0.15 11197-017 4.0 VS = 5V 16 11197-020 VS = 5V G = 100 VREF = 2.5V VIN- = 2.5V 4.5 OUTPUT VOLTAGE (V) 0.20 20 5.0 Figure 18. Input Bias Current vs. Common-Mode Voltage, VS = 15 V Rev. A | Page 12 of 24 0 0.1 1 10 100 1k FREQUENCY (Hz) Figure 21. Negative PSRR vs. Frequency Data Sheet AD8422 70 50 GAIN = 100 30 GAIN = 10 10 GAIN = 1 -10 10 100 1k 10k 100k FREQUENCY (Hz) 1M 10M -0.3 -0.4 10 20 30 40 50 60 70 80 90 100 Figure 25. Change in Input Offset Voltage (VOSI) vs. Warm-Up Time 0.4 2.0 GAIN = 1000 GAIN = 100 140 GAIN = 10 120 GAIN = 1 100 80 1 10 100 1k FREQUENCY (Hz) 10k 100k 11197-024 60 40 0.1 VS = 15V NORMALIZED AT 25C 1.5 INPUT BIAS CURRENT (nA) 160 CMRR (dB) -0.2 TIME (s) 180 Figure 23. CMRR vs. Frequency 0.3 1.0 0.2 0.5 0.1 0 0 -0.5 -0.1 -1.0 -0.2 -1.5 -0.3 -2.0 -40 -25 -10 5 20 35 50 65 80 95 110 -0.4 125 TEMPERATURE (C) Figure 26. Input Bias Current and Input Offset Current vs. Temperature 180 100 80 GAIN = 1000 GAIN = 10 100 GAIN = 1 GAIN ERROR (V/V) 120 REPRESENTATIVE SAMPLES NORMALIZED AT 25C 60 GAIN = 100 140 80 40 20 0 -20 -40 -60 60 -80 40 0.1 1 10 100 1k FREQUENCY (Hz) 10k 100k 11197-025 CMRR (dB) -0.1 0 Figure 22. Gain vs. Frequency 160 0 -0.5 11197-023 -20 0.1 INPUT OFFSET CURRENT (nA) 0 0.2 11197-027 20 0.3 Figure 24. CMRR vs. Frequency, 1 k Source Imbalance -100 -40 -25 -10 5 20 35 50 65 80 95 TEMPERATURE (C) Figure 27. Gain vs. Temperature (G = 1) Rev. A | Page 13 of 24 110 125 11197-028 GAIN (dB) 40 0.4 11197-026 CHANGE IN INPUT OFFSET VOLTAGE (V) 60 0.5 GAIN = 1000 AD8422 Data Sheet 50 +VS REPRESENTATIVE SAMPLE NORMALIZED AT 25C 20 10 0 -10 -20 -30 -1.0 -1.5 +1.5 +1.0 +0.5 -40 -25 -10 5 20 35 50 65 TEMPERATURE (C) 80 95 110 125 -VS 11197-029 -50 -40 -40C +25C +85C +105C +125C 0 6 8 10 12 14 16 18 Figure 31. Input Voltage Limit vs. Supply Voltage 0.50 +VS OUTPUT VOLTAGE SWING (V) REFERRED TO SUPPLY VOLTAGES 0.45 0.40 0.35 0.30 0.25 0.20 0.15 0.10 RL = 10k -0.1 -0.2 -0.3 +125C +85C +25C -40C +0.3 +0.2 -25 -10 5 20 35 50 65 80 95 110 125 TEMPERATURE (C) -VS 11197-030 0 -40 60 -0.2 OUTPUT VOLTAGE SWING (V) REFERRED TO SUPPLY VOLTAGES +VS ISHORT + 40 30 20 10 0 -10 ISHORT - -25 -10 5 20 35 50 65 TEMPERATURE (C) 6 8 10 12 14 16 18 RL = 2k -0.4 -0.6 +125C +85C +25C -40C -0.8 +0.8 +0.6 +0.4 +0.2 80 95 110 125 11197-031 -30 -40 4 Figure 32. Output Voltage Swing vs. Supply Voltage, RL = 10 k 70 -20 2 SUPPLY VOLTAGE (VS) Figure 29. Supply Current vs. Temperature (G = 1) 50 0 11197-035 +0.1 0.05 -VS 0 2 4 6 8 10 12 14 16 18 SUPPLY VOLTAGE (VS) Figure 33. Output Voltage Swing vs. Supply Voltage, RL = 2 k Figure 30. Short-Circuit Current vs. Temperature (G = 1) Rev. A | Page 14 of 24 11197-036 SUPPLY CURRENT (mA) 4 SUPPLY VOLTAGE (VS) Figure 28. CMRR vs. Temperature (G = 1), Normalized at 25C SHORT-CIRCUIT CURRENT (mA) 2 11197-034 30 CMRR (V/V) -0.5 INPUT VOLTAGE (V) REFERRED TO SUPPLY VOLTAGES 40 Data Sheet AD8422 10 15 8 GAIN NONLINEARITY (ppm) 5 -40C +25C +85C +105C +125C 0 -5 VS = 15V G = 10 6 4 2 0 -2 -4 -6 RL = 2k RL = 10k -8 1k 10k LOAD RESISTANCE () 100k -10 -10 11197-037 -15 100 -8 16 -0.4 12 NONLINEARITY (ppm) -0.2 -0.6 -40C +25C +85C +105C +125C +0.8 +0.6 0 2 4 6 8 10 4 0 -4 -8 -12 +0.2 -16 10m VS = 15V G = 100 8 +0.4 -20 -10 11197-038 OUTPUT VOLTAGE SWING (V) REFERRED TO SUPPLY VOLTAGES 20 1m OUTPUT CURRENT (A) -2 Figure 37. Gain Nonlinearity (G = 10) +VS -VS 100 -4 OUTPUT VOLTAGE (V) Figure 34. Output Voltage Swing vs. Load Resistance -0.8 -6 11197-040 -10 RL = 2k RL = 10k -8 -6 -4 -2 0 2 4 6 8 10 OUTPUT VOLTAGE (V) 11197-041 OUTPUT VOLTAGE SWING (V) 10 Figure 38. Gain Nonlinearity (G = 100) Figure 35. Output Voltage Swing vs. Output Current 50 5 40 VS = 15V G=1 VS = 15V G = 1000 30 NONLINEARITY (ppm) 3 2 1 0 -1 20 10 0 -10 -20 -2 -30 -3 -8 -6 -4 -2 0 2 4 OUTPUT VOLTAGE (V) 6 8 10 -50 -10 -8 -6 -4 -2 0 2 4 6 OUTPUT VOLTAGE (V) Figure 39. Gain Nonlinearity (G = 1000) Figure 36. Gain Nonlinearity (G = 1) Rev. A | Page 15 of 24 8 10 11197-042 -5 -10 RL = 2k RL = 10k -40 RL = 2k RL = 10k -4 11197-039 GAIN NONLINEARITY (ppm) 4 AD8422 Data Sheet G=1 100 5pA/DIV G = 10 G = 100 10 1 0.1 1 10 100 1k 10k 100k 11197-046 G = 1000 1s/DIV 11197-043 VOLTAGE NOISE RTI (nV/Hz) 1k FREQUENCY (Hz) Figure 40. Voltage Noise Spectral Density vs. Frequency Figure 43. 0.1 Hz to 10 Hz Current Noise 30 G = 1000, 100nV/DIV G=1 VS = 15V G = 1, 1V/DIV 15 10 5 11197-044 1s/DIV 20 VS = +5V 0 100 Figure 41. 0.1 Hz to 10 Hz RTI Voltage Noise (G = 1, G = 1000) 1k 10k FREQUENCY (Hz) 100k 1M 11197-047 OUTPUT VOLTAGE (V p-p) 25 Figure 44. Large Signal Frequency Response 5V/DIV 1k 13.6s TO 0.01% 15.2s TO 0.001% 100 10s/DIV 10 1 10 100 FREQUENCY (Hz) 1k Figure 42. Current Noise Spectral Density vs. Frequency 10k 11197-048 0.002%/DIV 11197-045 CURRENT NOISE (fA/Hz) 10k Figure 45. Large Signal Pulse Response and Settling Time (G = 1), 10 V Step, VS = 15 V, RL = 2 k, CL = 100 pF Rev. A | Page 16 of 24 Data Sheet AD8422 30 RL = 2k CL = 100pF 25 SETTLING TIME (s) 5V/DIV 12.8s TO 0.01% 15.1s TO 0.001% 0.002%/DIV 20 SETTLED TO 0.001% 15 10 SETTLED TO 0.01% 0 2 4 6 8 10 12 14 16 18 20 STEP SIZE (V) Figure 46. Large Signal Pulse Response and Settling Time (G = 10), 10 V Step, VS = 15 V, RL = 2 k, CL = 100 pF 11197-052 10s/DIV 11197-049 5 Figure 49. Settling Time vs. Step Size (G = 1) 5V/DIV 50mV/DIV 12.0s TO 0.01% 15.2s TO 0.001% 10s/DIV 11197-053 10s/DIV 11197-050 0.002%/DIV Figure 50. Small Signal Pulse Response (G = 1), RL = 2 k, CL = 100 pF Figure 47. Large Signal Pulse Response and Settling Time (G = 100), 10 V Step, VS = 15 V, RL = 2 k, CL = 100 pF 5V/DIV 20mV/DIV 80s TO 0.01% 160s TO 0.001% 10s/DIV Figure 48. Large Signal Pulse Response and Settling Time (G = 1000), 10 V Step, VS = 15 V, RL = 2 k, CL = 100 pF 11197-054 100s/DIV 11197-051 0.002%/DIV Figure 51. Small Signal Pulse Response (G = 10), RL = 2 k, CL = 100 pF Rev. A | Page 17 of 24 AD8422 Data Sheet NO LOAD 20 pF 50 pF 100 pF 50mV/DIV Figure 52. Small Signal Pulse Response (G = 100), RL = 2 k, CL = 100 pF Figure 54. Small Signal Pulse Response with Various Capacitive Loads (G = 1), RL = No Load 11197-056 20mV/DIV 100s/DIV 10s/DIV 11197-057 10s/DIV 11197-055 20mV/DIV Figure 53. Small Signal Pulse Response (G = 1000), RL = 2 k, CL = 100 pF Rev. A | Page 18 of 24 Data Sheet AD8422 THEORY OF OPERATION +VS I VB IB COMPENSATION A1 IB COMPENSATION A2 C1 10k +VS C2 10k NODE 1 -IN ESD AND OVERVOLTAGE PROTECTION R1 Q1 9.9k super 10k R2 9.9k +VS +VS RG NODE 3 -VS OUTPUT A3 NODE 2 Q2 super ESD AND OVERVOLTAGE PROTECTION NODE 4 +VS -VS 10k REF +IN -VS -VS 11197-058 I DIFFERENCE AMPLIFIER STAGE Figure 55. Simplified Schematic The transfer function of the AD8422 is ARCHITECTURE The AD8422 is based on the classic 3-op-amp instrumentation amplifier topology. This topology has two stages: a preamplifier to provide differential amplification followed by a difference amplifier that removes the common-mode voltage. Figure 55 shows a simplified schematic of the AD8422. Topologically, Q1, A1, R1 and Q2, A2, R2 can be viewed as precision current feedback amplifiers that maintain a fixed current in the emitters of Q1 and Q2. Any change in the input signal forces the output voltages of A1 and A2 to change accordingly and maintain the Q1 and Q2 current at the correct value. This causes a precise diode drop from -IN and +IN to Node 3 and Node 4, respectively, so that the differential signal applied to the inputs is replicated across the RG pins. Any current through RG must also flow through R1 and R2, creating the gained differential voltage between Node 1 and Node 2. The amplified differential signal and the common-mode signal are applied to a difference amplifier that rejects the commonmode voltage but preserves the amplified differential voltage. Laser-trimmed resistors allow for a highly accurate in-amp with a gain error of less than 0.01% and a CMRR that exceeds 94 dB (G = 1). The supply current is precisely trimmed to reduce uncertainties due to part-to-part variations in power dissipation and noise. The high performance pinout and special attention to design and layout allow for high CMRR across a wide frequency and temperature range. Using superbeta input transistors and bias current compensation, the AD8422 offers extremely high input impedance and low bias current, as well as very low voltage noise while using only 300 A supply current. The overvoltage protection scheme allows the input to go 40 V from the opposite rail at all gains without compromising the noise performance. VOUT = G x (VIN+ - VIN-) + VREF where: G = 1+ 19.8 k RG GAIN SELECTION Placing a resistor across the RG terminals sets the gain of the AD8422 that can be calculated by referring to Table 6 or by using the following gain equation: RG = 19.8 k G -1 The AD8422 defaults to G = 1 when no gain resistor is used. Add the tolerance and gain drift of the RG resistor to the specifications of the AD8422 to determine the total gain accuracy of the system. When the gain resistor is not used, gain error and gain drift are minimal. Table 6. Gains Achieved Using 1% Resistors 1% Standard Table Value of RG () Calculated Gain 19.6 k 4.99 k 2.21 k 1.05 k 402 200 100 39.2 20 2.010 4.968 9.959 19.86 50.25 100.0 199.0 506.1 991.0 Rev. A | Page 19 of 24 AD8422 Data Sheet RG Power Dissipation 1 8 +VS RG 2 7 VOUT RG 3 6 REF +IN 4 5 -VS REFERENCE TERMINAL The output voltage of the AD8422 is developed with respect to the potential on the reference terminal. This can be used to apply a precise offset to the output signal. For example, a voltage source can be tied to the REF pin to level shift the output, allowing the AD8422 to drive a unipolar analog-to-digital converter (ADC). The REF pin is protected with ESD diodes and must not exceed either +VS or -VS by more than 0.3 V. For best performance, maintain a source impedance to the REF terminal that is below 1 . As shown in Figure 55, the reference terminal, REF, is at one end of a 10 k resistor. Additional impedance at the REF terminal adds to this 10 k resistor and results in amplification of the signal connected to the positive input. The amplification from the additional RREF can be calculated as 2(10 k + RREF)/(20 k + RREF) Only the positive signal path is amplified; the negative path is unaffected. This uneven amplification degrades CMRR. CORRECT AD8422 REF Common-Mode Rejection Ratio over Frequency Poor layout can cause some of the common-mode signals to be converted to differential signals before reaching the in-amp. Such conversions occur when one input path has a frequency response that is different from the other. To maintain high CMRR over frequency, closely match the input source impedance and capacitance of each path. Place additional source resistance in the input path (for example, for input protection) close to the in-amp inputs, which minimizes their interaction with parasitic capacitance from the PCB traces. Parasitic capacitance at the gain setting pins (RG) can also affect CMRR over frequency. If the board design has a component at the gain setting pins (for example, a switch or jumper), choose a component such that the parasitic capacitance is as small as possible. Use a stable dc voltage to power the instrumentation amplifier. Noise on the supply pins can adversely affect performance. REF V + 11197-059 OP1177 - Figure 57. Pinout Diagram Power Supplies and Grounding AD8422 V TOP VIEW (Not to Scale) Figure 56. Driving the Reference Pin (REF) INPUT VOLTAGE RANGE The 3-op-amp architecture of the AD8422 applies gain in the first stage before removing common-mode voltage with the difference amplifier stage. Internal nodes between the first and second stages (Node 1 and Node 2 in Figure 55) experience a combination of a gained signal, a common-mode signal, and a diode drop. The voltage supplies can limit the combined signal, even when the individual input and output signals are not limited. Figure 10 through Figure 13 show this limitation in detail. Place a 0.1 F capacitor as close as possible to each supply pin. Because the length of the bypass capacitor leads is critical at high frequency, surface-mount capacitors are recommended. A parasitic inductance in the bypass ground trace works against the low impedance created by the bypass capacitor. As shown in Figure 58, a 10 F capacitor can be used farther away from the device. For larger value capacitors, intended to be effective at lower frequencies, the current return path distance is less critical. In most cases, this capacitor can be shared by other local precision integrated circuits. +VS 0.1F 10F +IN RG VOUT AD8422 LOAD LAYOUT REF -IN To ensure optimum performance of the AD8422 at the PCB level, take care in the design of the board layout. To aid in this task, the pins of the AD8422 are arranged in a logical manner. 0.1F -VS 10F 11197-061 INCORRECT AD8422 -IN 11197-060 The AD8422 duplicates the differential voltage across its inputs onto the RG resistor. Choose an RG resistor size that is sufficient to handle the expected power dissipation at ambient temperature. Figure 58. Supply Decoupling, REF, and Output Referred to Local Ground Rev. A | Page 20 of 24 Data Sheet AD8422 INPUT VOLTAGES BEYOND THE SUPPLY RAILS A ground plane layer is helpful to reduce parasitic inductances. This minimizes voltage drops with changes in current. The area of the current path is directly proportional to the magnitude of parasitic inductances and, therefore, the impedance of the path at high frequencies. Large changes in currents in an inductive decoupling path or ground return create unwanted effects due to the coupling of such changes into the amplifier inputs. Many instrumentation amplifiers specify excellent CMRR and input impedance, but in a real system, the performance suffers because of the external components required for input protection. The AD8422 has very robust inputs. It typically does not need additional input protection. Input voltages can be up to 40 V from the opposite supply rail without damage to the part. For example, with a +5 V positive supply and a 0 V negative supply, the part can safely withstand voltages from -35 V to +40 V. Unlike some other instrumentation amplifiers, the part can handle large differential input voltages even when the part is in high gain. Because load currents flow from the supplies, connect the load at the same physical location as the bypass capacitor grounds. Reference Pin The output voltage of the AD8422 is developed with respect to the potential on the reference terminal. Ensure that REF is tied to the appropriate local ground. +VS VIN+ - INPUT BIAS CURRENT RETURN PATH The input bias current of the AD8422 must have a dc return path to ground. When using a floating source without a current return path, such as a thermocouple, create a current return path, as shown in Figure 59. INCORRECT + VIN+ - For input voltages less than 40 V from the opposite rail, no input protection is required. Keep the rest of the AD8422 terminals within the supplies. All terminals of the AD8422 are protected against ESD. AD8422 REF Input Voltages Beyond the Maximum Ratings REF -VS For applications where the AD8422 encounters voltages beyond the limits in the Absolute Maximum Ratings section, external protection is required. This external protection depends on the duration of the overvoltage event and the noise performance required. -VS TRANSFORMER TRANSFORMER +VS -VS Figure 60. Input Overvoltage Protection with no External Components +VS AD8422 AD8422 MOST APPLICATIONS CORRECT +VS I 11197-063 + +VS For short-lived events, transient protectors such as metal oxide varistors (MOVs) may be all that is required. AD8422 For longer events, use resistors in series with the inputs combined with diodes. To avoid worsening bias current performance, low leakage diodes, such as the BAV199 or FJH1100s, are recommended. The diodes prevent the voltage at the input of the amplifier from exceeding the maximum ratings, while the resistors limit the current into the diodes. Because most external diodes can easily handle 100 mA or more, resistor values do not have to be large. Therefore, the protection resistance has minimal impact on noise performance. AD8422 REF REF 10M -VS -VS THERMOCOUPLE THERMOCOUPLE +VS +VS C C C R 1 fHIGH-PASS = 2RC AD8422 REF AD8422 C REF -VS CAPACITIVELY COUPLED -VS CAPACITIVELY COUPLED 11197-062 R Figure 59. Creating an Input Bias Current Return Path Rev. A | Page 21 of 24 AD8422 Data Sheet + + I VIN+ - RPROTECT AD8422 RADIO FREQUENCY INTERFERENCE (RFI) +VS RF rectification is often a problem when amplifiers are used in applications that have strong RF signals. The disturbance can appear as a small dc offset voltage. High frequency signals can be filtered with a low-pass RC network placed at the input of the instrumentation amplifier, as shown in Figure 62. I VIN+ - AD8422 RPROTECT + -VS TRANSIENT PROTECTION RPROTECT + VIN+ - +VS I AD8422 +VS SIMPLE CONTINUOUS PROTECTION +VS RPROTECT + VIN+ - 0.1F +VS I -VS +VS -VS LOW NOISE CONTINUOUS OPTION 1 + VIN- - R AD8422 +IN 2k CD 10nF RG REF 2k -IN CC 1nF 0.1F Figure 61. Input Protection Options for Input Voltages Beyond Absolute Maximum Ratings At the expense of some noise performance, another solution is to use series resistors. In the overvoltage case, current into the inputs of the AD8422 is internally limited to a safe value for the amplifier. Although the AD8422 inputs must still be kept within the Absolute Maximum Ratings, the I x R drop across the protection resistor increases the maximum voltage that the system can withstand to the following values: For positive input signals, VMAX_NEW = (40 V + Negative Supply) + IIN x RPROTECT For negative input signals, VMIN_NEW = (Positive Supply - 40 V) - IOUT x RPROTECT Overvoltage performance is shown in Figure 14, Figure 15, Figure 16, and Figure 17. With gains greater than 100 and supply voltages less than 2.5 V, overdrive voltages beyond the rails may cause the output to invert as far as the REF pin voltage. VOUT AD8422 R -VS -VS LOW NOISE CONTINUOUS OPTION 2 10F CC 1nF RPROTECT RPROTECT + VIN- - -VS VIN- - 11197-064 VIN- - + 10F -VS 11197-065 +VS Figure 62. RFI Suppression The filter limits the input signal bandwidth, according to the following relationship: FilterFrequency DIFF = FilterFrequencyCM = 1 2R(2C D + CC ) 1 2RCC where CD 10 CC. CD affects the difference signal, and CC affects the common-mode signal. Choose values of R and CC that minimize RFI. A mismatch between R x CC at the positive input and R x CC at the negative input degrades the CMRR of the AD8422. By using a value of CD that is one order of magnitude larger than CC, the effect of the mismatch is reduced, and performance is improved. Resistors add noise; therefore, the choice of the resistor and capacitor values depends on the desired tradeoff between noise, input impedance at high frequencies, and RF immunity. The resistors used for the RFI filter can be the same as those used for input protection. Rev. A | Page 22 of 24 Data Sheet AD8422 APPLICATIONS INFORMATION ADA4096-2, ensure that the desired output voltage of the AD8276 is within its output range, and VL is within the input and output range of the ADA4096-2. The transistor must have sufficient breakdown voltage and IC. Low cost transistors, such as the BC847 or 2N5210, are recommended. PRECISION BRIDGE CONDITIONING With its high CMRR, low drift, and rail-to-rail output, the AD8422 is an excellent choice for conditioning a signal from a Wheatstone bridge. With appropriate supply voltages, the gain and reference pin voltage can be adjusted to match the full-scale bridge output to any desired output range, such as 0 V to 5 V. Figure 63 shows a circuit to convert a bridge signal into a 4 mA to 20 mA output using the AD8276 low power, precision difference amplifier, and the ADA4096-2 low power, rail-to-rail input and output, overvoltage protected op amp. With high precision bridge circuits, care must be taken to compensate offsets and temperature errors. For example, if the voltage at the REF pin is used to compensate for the bridge offset, ensure that the AD8422 is within its operating range for the maximum expected offset. If the zeroadjust potentiometer is excluded, connect the positive op amp input to the center of the 24.9 k, 10.7 k divider, which is at 1.5 V. If lower supply voltages are used for the AD8276 and the PROCESS CONTROL ANALOG INPUT In process control systems such as programmable logic controllers (PLC) and distributed control systems (DCS), analog variables typically occur in just a few standard voltage or current ranges, including 4 mA to 20 mA and 10 V. Variables within these input ranges must often be gained or attenuated and level shifted to match a specific ADC input range such as 0 V to 5 V. The circuit in Figure 64 shows one way this can be done with a single AD8422. Low power, overvoltage protection, and high precision make the AD8422 a good match for process control applications, and high input impedance, low bias current, and low current noise allow significant source resistance with minimum additional errors. +5V +5V +IN VOUT_FS = 15mV RG +24V AD8422 +5V REF -IN RG = 301 G = 66.8V/V AD8276 24.9k +24V SENSE +IN V = 0.5V TO 2.5V +24V VOUT REF -IN +24V 1 124 IOUT = 4mA TO 20mA VL 10.7k ADA4096-2 RL 11197-066 ADA4096-2 1OPTIONAL ZERO ADJUST Figure 63. Bridge Circuit with 4 mA to 20 mA Output TERMINAL BLOCK 0V TO 10V, 10V 42.2k 0V TO 5V, 5V 34k 8.45k 49.9 +IN RG VOUT = 2.5V 2.5V AD8422 1k -IN REF 2.5V -15V RG = 13.2k G = 2.5V/V Figure 64. Process Control Analog Input Rev. A | Page 23 of 24 11197-067 4mA TO 20mA, 0mA TO 20mA 20mA +15V 1k 0V TO 1V, 1V AD8422 Data Sheet OUTLINE DIMENSIONS 5.00 (0.1968) 4.80 (0.1890) 4.00 (0.1574) 3.80 (0.1497) 8 5 1 6.20 (0.2441) 5.80 (0.2284) 4 1.27 (0.0500) BSC 0.25 (0.0098) 0.10 (0.0040) 1.75 (0.0688) 1.35 (0.0532) 0.51 (0.0201) 0.31 (0.0122) COPLANARITY 0.10 SEATING PLANE 0.50 (0.0196) 0.25 (0.0099) 45 8 0 0.25 (0.0098) 0.17 (0.0067) 1.27 (0.0500) 0.40 (0.0157) 012407-A COMPLIANT TO JEDEC STANDARDS MS-012-AA CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS (IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN. Figure 65. 8-Lead Standard Small Outline Package [SOIC_N] Narrow Body (R-8) Dimensions shown in millimeters and (inches) 3.20 3.00 2.80 8 3.20 3.00 2.80 1 5.15 4.90 4.65 5 4 PIN 1 IDENTIFIER 0.65 BSC 0.95 0.85 0.75 15 MAX 1.10 MAX 0.40 0.25 6 0 0.23 0.09 COMPLIANT TO JEDEC STANDARDS MO-187-AA 0.80 0.55 0.40 10-07-2009-B 0.15 0.05 COPLANARITY 0.10 Figure 66. 8-Lead Mini Small Outline Package [MSOP] (RM-8) Dimensions shown in millimeters ORDERING GUIDE Model1 AD8422ARZ AD8422ARZ-R7 AD8422ARZ-RL AD8422BRZ AD8422BRZ-R7 AD8422BRZ-RL AD8422ARMZ AD8422ARMZ-R7 AD8422ARMZ-RL AD8422BRMZ AD8422BRMZ-R7 AD8422BRMZ-RL 1 Temperature Range -40C to +85C -40C to +85C -40C to +85C -40C to +85C -40C to +85C -40C to +85C -40C to +85C -40C to +85C -40C to +85C -40C to +85C -40C to +85C -40C to +85C Package Description 8-Lead SOIC_N, Standard Grade 8-Lead SOIC_N, Standard Grade, 7" Tape and Reel, 8-Lead SOIC_N, Standard Grade, 13" Tape and Reel 8-Lead SOIC_N, High Performance Grade 8-Lead SOIC_N, High Performance Grade, 7" Tape and Reel 8-Lead SOIC_N, High Performance Grade, 13" Tape and Reel 8-Lead MSOP, Standard Grade 8-Lead MSOP, Standard Grade, 7" Tape and Reel, 8-Lead MSOP, Standard Grade, 13" Tape and Reel 8-Lead MSOP, High Performance Grade 8-Lead MSOP, High Performance Grade, 7" Tape and Reel 8-Lead MSOP, High Performance Grade, 13" Tape and Reel Z = RoHS Compliant Part. (c)2013-2015 Analog Devices, Inc. All rights reserved. Trademarks and registered trademarks are the property of their respective owners. D11197-0-1/15(A) Rev. A | Page 24 of 24 Package Option R-8 R-8 R-8 R-8 R-8 R-8 RM-8 RM-8 RM-8 RM-8 RM-8 RM-8 Branding Y4U Y4U Y4U Y4V Y4V Y4V