TDA2030A
18W Hi-Fi AMPLIFIER AND 35W DRIVER
March 1995
PENTAWATT
ORDERING NUMBERS : TDA2030AH
TDA2030AV
DESCRIPTION
The TDA2030Ais a monolithic IC in Pentawatt
package intended for use as low frequency class
AB amplifier.
With VS max = 44V it is particularlysuited for more
reliable applications without regulated supply and
for 35W driver circuits using low-cost complemen-
tary pairs.
The TDA2030A provides high output current and
hasvery lowharmonicand cross-overdistortion.
Further the device incorporatesa short circuit pro-
tection system comprising an arrangement for
automaticallylimiting the dissipated powersoas to
keep the working point of the output transistors
within their safe operating area. A conventional
thermalshut-down system is also included.
TYPICAL APPLICATION
1/15
TEST CIRCUIT
PIN CONNECTION (Top view)
THERMAL DATA
Symbol Parameter Value Unit
Rth (j-case) Thermal Resistance Junction-case Max 3 °C/W
TDA2030A
2/15
ABSOLUTE MAXIMUM RATINGS
Symbol Parameter Value Unit
VsSupply Voltage ±22 V
ViInput Voltage Vs
ViDifferential Input Voltage ±15 V
IoPeak Output Current (internallylimited) 3.5 A
Ptot Total Power Dissipation at Tcase =90°C20 W
Tstg,T
jStorage and Junction Temperature – 40 to + 150 °C
ELECTRICAL CHARACTERISTICS
(Refer to the test circuit, VS=±16V,Tamb =25oC unless otherwise specified)
Symbol Parameter Test Conditions Min. Typ. Max. Unit
VsSupply Voltage ±6±22 V
IdQuiescent Drain Current 50 80 mA
IbInput Bias Current VS=±22V 0.2 2 µA
Vos Input Offset Voltage VS=±22V ±2±20 mV
Ios Input Offset Current ±20 ±200 nA
POOutput Power d = 0.5%, Gv= 26dB
f = 40 to 15000Hz RL=4Ω
R
L=8Ω
V
S=±19V RL=8Ω
15
10
13
18
12
16
W
BW Power Bandwidth Po= 15W RL=4Ω100 kHz
SR Slew Rate 8 V/µsec
GvOpen Loop Voltage Gain f = 1kHz 80 dB
GvClosed Loop Voltage Gain f = 1kHz 25.5 26 26.5 dB
d Total Harmonic Distortion Po= 0.1 to 14W RL=4Ω
f = 40 to 15 000Hz f = 1kHz
Po= 0.1 to 9W, f = 40 to 15 000Hz
RL=8Ω
0.08
0.03
0.5
%
%
%
d2Second Order CCIF Intermodulation
Distortion PO= 4W, f2–f
1= 1kHz, RL=4Ω0.03 %
d3Third Order CCIF Intermodulation
Distortion f1= 14kHz, f2= 15kHz
2f1–f
2= 13kHz 0.08 %
eNInput Noise Voltage B = Curve A
B = 22Hz to 22kHz 2
310µV
µV
i
NInput Noise Current B = Curve A
B = 22Hz to 22kHz 50
80 200 pA
pA
S/N Signal to Noise Ratio RL=4Ω,R
g= 10kΩ, B = Curve A
PO= 15W
PO=1W 106
94 dB
dB
RiInput Resistance (pin 1) (open loop) f = 1kHz 0.5 5 MΩ
SVR Supply Voltage Rejection RL=4Ω,R
g= 22kΩ
Gv= 26dB, f = 100 Hz 54 dB
TjThermal Shut-down Junction
Temperature 145 °C
TDA2030A
3/15
Figure 3 : Output Powerversus Supply Voltage
Figure 4 : Total Harmonic Distortion versus
Output Power(test using rise filters)
Figure 1 : Single Supply Amplifier
Figure 2 : Open Loop-frequencyResponse
Figure 5 : Two Tone CCIF Intremodulation
Distortion
TDA2030A
4/15
Figure 6 : Large Signal Frequency Response Figure 7 : Maximum Allowable Power Dissipation
versus Ambient Temperature
Figure 10 : Output Power versus Input Level Figure 11 : Power Dissipation versus Output
Power
Figure 8 : Output Power versus Supply Voltage Figure 9 : TotalHarmonicDistortion versus
OutputPower
TDA2030A
5/15
Figure 12 : Single Supply High Power Amplifier (TDA2030A+ BD907/BD908)
Figure 13 : P.C. Boardand Component Layout for the Circuit of Figure 12 (1:1 scale)
TDA2030A
6/15
TYPICAL PERFORMANCE OF THE CIRCUIT OF FIGURE 12
Symbol Parameter Test Conditions Min. Typ. Max. Unit
VsSupply Voltage 36 44 V
IdQuiescent Drain Current Vs= 36V 50 mA
PoOutput Power d = 0.5%, RL=4Ω, f = 40 z to 15Hz
Vs= 39V
Vs= 36V
d = 10%, RL=4Ω, f = 1kHz
Vs= 39V
Vs= 36V
35
28
44
35
W
W
W
W
GvVoltage Gain f = 1kHz 19.5 20 20.5 dB
SR Slew Rate 8 V/µsec
d Total Harmonic Distortion f = 1kHz
Po= 20W f = 40Hz to 15kHz 0.02
0.05 %
%
ViInput Sensitivity Gv= 20dB, f = 1kHz, Po= 20W, RL=4Ω890 mV
S/N Signal to Noise Ratio RL=4Ω,R
g= 10kΩ, B = Curve A
Po= 25W
Po=4W 108
100
dB
Figure 14 : Typical Amplifier with Spilt Power Supply
Figure 15 : P.C. Boardand Component Layout for the Circuit of Figure 14 (1:1 scale)
TDA2030A
7/15
Figure 16 : BridgeAmplifier with Split Power Supply (PO= 34W, VS=±16V)
Figure 17 : P.C. Boardand ComponentLayout for the Circuit of Figure16 (1:1 scale)
MULTIWAY SPEAKER SYSTEMSAND ACTIVE
BOXES
Multiway loudspeaker systems provide the best
possible acoustic performance since each loud-
speaker is specially designed and optimized to
handle a limited range of frequencies.Commonly,
these loudspeakersystems divide theaudio spec-
trum into two or three bands.
Tomaintain aflatfrequencyresponseovertheHi-Fi
audio range the bands covered by each loud-
speakermust overlap slightly. Imbalance between
the loudspeakers produces unacceptable results
therefore it is important to ensure that each unit
generates the correct amount of acoustic energy
for its segmento of the audio spectrum. In this
respect it is also important to know the energy
distribution ofthe music spectrumto determinethe
cutoff frequenciesof the crossoverfilters (see Fig-
ure 18). As an examplea 100Wthree-way system
with crossover frequencies of 400Hz and 3kHz
would require 50W for the woofer, 35W for the
midrange unitand 15W for thetweeter.
TDA2030A
8/15
Figure 18 : Power Distribution versus Frequency
Both active and passive filters can be used for
crossoversbut todayactivefilters cost significantly
less than a good passive filter using air cored
inductors and non-electrolyticcapacitors. In addi-
tion, active filters do not suffer from the typical
defectsof passive filters:
- power less
- increased impedance seen by the loudspeaker
(lowerdamping)
- difficulty of precise design due to variable loud-
speaker impedance.
Obviously,active crossovers can only be used if a
poweramplifieris provided for eachdrive unit. This
makes it particularly interesting and economically
sound to use monolithic power amplifiers.
In someapplications, complex filters are not really
necessaryand simple RC low-passand high-pass
networks(6dB/octave)can be recommended.
The result obtained are excellent because this is
the best type of audio filter and the only one free
from phaseand transientdistortion.
The rather poor out of band attenuation of single
RC filters means that the loudspeakermust oper-
ate linearlywell beyondthe crossoverfrequencyto
avoid distortion.
Figure 19 : ActivePower Filter
A more effective solution, named ”Active Power
Filter” by SGS-THOMSON is shown in Figure 19.
The proposed circuit can realizecombined power
amplifiers and 12dB/octave or 18dB/octave high-
pass or low-pass filters.
In practice, at the input pins of the amplifier two
equal and in-phase voltages are available, as re-
quired for the active filter operation.
Theimpedanceatthepin(-)isoftheorderof100Ω,
while that of the pin (+) is very high, which is also
whatwas wanted.
The component values calculated for fc= 900Hz
using a Bessek3rd order Sallen and Key structure
are :
C1=C
2=C
3R
1R
2R
3
22nF 8.2kΩ5.6kΩ33kΩ
Usingthistypeof crossoverfilter,acomplete3-way
60W active loudspeaker system is shown in Fig-
ure 20.
It employs 2nd order Buttherworth filters with the
crossover frequenciesequal to 300Hz and 3kHz.
The midrange section consistsof two filters, ahigh
pass circuit followed by a low pass network. With
VS= 36V the output power delivered to the woofer
is 25W at d = 0.06% (30Wat d = 0.5%).
The power delivered to the midrange and the
tweeter can be optimized in the design phase
taking in account the loudspeaker efficiency and
impedance(RL=4Ωto 8Ω).
It is quite common that midrange and tweeter
speakers have an efficiency 3dB higher than-
woofers.
TDA2030A
9/15
Figure 20 : 3 Way 60W ActiveLoudspeakerSystem (VS= 36V)
TDA2030A
10/15
MUSICALINSTRUMENTS AMPLIFIERS
Another important field of application for active
systemsis music.
In this area the use of several medium power
amplifiers is more convenient than a single high
poweramplifier, and it is also more realiable.
A typical example (see Figure 21) consist of four
amplifiers each driving a low-cost, 12 inch loud-
speaker. This application can supply 80 to
160WRMS.
Figure 21 : High Power Active Box
for Musical Instrument
TRANSIENT INTERMODULATION DISTOR-
TION (TIM)
Transient intermodulationdistortion is an unfortu-
nate phenomen associated with negative-feed-
back amplifiers. When a feedback amplifier
receives an input signal which rises very steeply,
i.e.containshigh-frequencycomponents,thefeed-
back can arrive too late so that the amplifiers
overloads anda burstof intermodulationdistortion
will be produced as in Figure 22. Since transients
occur frequentlyin music this obviouslya problem
for the designerof audio amplifiers.Unfortunately,
heavy negative feedback is frequency used to re-
duce the total harmonic distortion of an amplifier,
which tends to aggravate the transientintermodu-
lation (TIM situation. The best known method for
the measurement of TIM consists of feeding sine
waves superimposed onto square waves, into the
amplifier under test. The output spectrum is then
examined using a spectrum analyser and com-
paredtotheinput.Thismethodsuffersfromserious
disadvantages: the accuracy is limited, the meas-
urement is a rather delicate operation and an ex-
pensive spectrum analyser is essential. A new
approach (see Technical Note 143) applied by
SGS-THOMSONto monolithicamplifiersmeasure-
mentis fast cheap-itrequiresnothingmore sophis-
ticatedthanan oscilloscope- andsensitive- and it
can be useddown to the valuesas low as 0.002%
in highpower amplifiers.
Figure 22 : OvershootPhenomenonin Feedback
Amplifiers
The ”inverting-sawtooh” method of measurement
isbasedon theresponseof anamplifier toa 20kHz
sawtooth waveform. The amplifier has no difficulty
following the slow ramp but itcannot follow thefast
edge. The output will follow the upper line in Fig-
ure 23cutting oftheshadedarea andthusincreas-
ing themean level.If this outputsignal is filtered to
remove thesawtooth,directvoltageremainswhich
indicates the amountof TIM distortion, although it
is difficult to measure because it is indistinguish-
able from the DC offset of the amplifier. This prob-
lem is neatly avoided in the IS-TIM method by
periodically inverting the sawtooth waveform at a
low audio frequencyas shown in Figure 24.
Figure 23 : 20kHzSawtoothWaveform
Figure 24 : Inverting SawtoothWaveform
TDA2030A
11/15
In the case of the sawtoothin Figure 25 the mean
level was increased by the TIM distortion, for a
sawtooth inthe other direction the oppositeis true.
The result is an AC signal at the output whole
peak-to-peakvalue is the TIM voltage, which can
be measured easily with an oscilloscope. If the
peak-to-peakvalue of the signal and the peak-to-
peak of the inverting sawtooth are measured,the
TIM can be found very simply from:
TIM =VOUT
Vsawtooth ⋅100
In Figure25 theexperimentalresultsareshownfor
the 30Wamplifier using the TDA2030Aas a driver
and a low-cost complementary pair. A simple RC
filter on the input of the amplifier to limit the maxi-
mumsignalslope (SS)isaneffectivewayto reduce
TIM.
Figure 25 : TIM Distortion versus Output Power
The diagram of Figure 26 originated by SGS-
THOMSONcanbeusedto findtheSlew-Rate(SR)
requiredfor a given output power or voltageand a
TIM design target.
For example if an anti-TIM filter with a cutoff at
30kHz is used and the max. peak-to-peak output
voltage is 20V then, referring to the diagram, a
Slew-Rate of 6V/µs is necessaryfor 0.1%TIM.
As shown Slew-Rates of above 10V/µs do not
contributeto a furtherreductionin TIM.
Slew-Ratesof100/µs arenot onlyuseless butalso
a disadvantage in Hi-Fi audio amplifiers because
they tend to turnthe amplifierinto a radio receiver.
Figure 26 : TIM DesignDiagram (fC= 30kHz)
POWER SUPPLY
Usingmonolithicaudioamplifierwith non-regulated
supply voltage it is important to designthe power
supply correctly. In any working case it must pro-
vide asupplyvoltageless than the maximumvalue
fixed by the IC break-downvoltage.
It is essential to take into account all the working
conditions,inparticularmainsfluctuationsandsup-
ply voltage variations with and without load. The
TDA2030A(VSmax=44V) isparticularlysuitablefor
substitution of the standard IC power amplifiers
(with VS max = 36V) for more reliableapplications.
An example, using a simple full-wave rectifier fol-
lowed by a capacitorfilter, is shown in the table 1
and in thediagramof Figure 27.
Figure27 : DCCharacteristicsof
50W Non-regulatedSupply
TDA2030A
12/15
Table 2
Comp. Recom.
Value Purpose Larger than
Recommended Value Smaller than
Recommended Value
R1 22kΩClosed loop gain setting Increase of gain Decrease of gain
R2 680ΩClosed loop gain setting Decrease of gain (*) Increase of gain
R3 22kΩNon inverting input biasing Increase of input impedance Decrease of input impedance
R4 1ΩFrequency Stability Danger of oscillation at high
frequencies with inductive
loads
R5 ≅3R2 Upper Frequency Cut-off Poor High Frequencies
Attenuation Danger of Oscillation
C1 1µFInput DC Decoupling Increase of low frequencies
cut-off
C2 22µFInverting DC Decoupling Increase of low frequencies
cut-off
C3, C4 0.1µFSupply Voltage Bypass Danger of Oscillation
C5, C6 100µFSupply Voltage Bypass Danger of Oscillation
C7 0.22µFFrequency Stability Larger Bandwidth
C8 ≈1
2πBR1 Upper Frequency Cut-off Smaller Bandwidth Larger Bandwidth
D1, D2 1N4001 To protect the device against output voltage spikes
Table 1
Mains
(220V) Secondary
Voltage DC OutputVoltage (Vo)
Io=0 I
o= 0.1A Io=1A
+ 20% 28.8V 43.2V 42V 37.5V
+ 15% 27.6V 41.4V 40.3V 35.8V
+ 10% 26.4V 39.6V 38.5V 34.2V
– 24V 36.2V 35V 31V
– 10% 21.6V 32.4V 31.5V 27.8V
– 15% 20.4V 30.6V 29.8V 26V
– 20% 19.2V 28.8V 28V 24.3V
Aregulatedsupplyisnot usuallyusedforthepower
outputstagesbecauseof its dimensioningmust be
donetaking intoaccountthe power to supply in the
signal peaks.They are only a smallpercentage of
the total music signal, with consequently large
overdimensioningof the circuit.
Evenif with a regulatedsupplyhigheroutputpower
canbeobtained(VSis constantin all working condi-
tions), the additionalcost and power dissipation do
notusually justify itsuse. Usingnon-regulatedsup-
plies, there are fewer designe restriction. In fact,
when signal peaks are present, the capacitor filter
actsas a flywheel supplyingthe required energy.
In average conditions, the continuouspower sup-
pliedis lower. The music power/continuouspower
ratio is greater in this case than for the case of
regulated supplied, with space saving and cost
reduction.
(*) The value of closed loop gain must be higher than 24dB.
APPLICATION SUGGESTION
The recommendedvalues of the componentsare
those shown on application circuit of Figure 14.
Differentvaluescan be used.The Table2 can help
the designer.
SHORT CIRCUIT PROTECTION
The TDA2030Ahas an original circuit which limits
the current of the output transistors. This function
can be considered as being peak power limiting
rather than simple current limiting. It reduces the
possibilitythat the devicegets damaged duringan
accidentalshort circuit from AC output to ground.
THERMAL SHUT-DOWN
The presenceofa thermallimiting circuit offersthe
followingadvantages:
1. An overload on the output (even if it is
permanent), or an above limit ambient
temperaturecan be easily supported since the
Tjcannotbe higher than 150oC.
2. The heatsink can have a smaller factor of
safety compared with that of a conventional
circuit. There isnopossibility ofdevicedamage
due to high junction temperature. If for any
reason, the junctiontemperatureincreases up
to 150oC, the thermal shut-down simply
reduces the power dissipationand the current
consumption.
TDA2030A
13/15
L2
L3
L5
L7
L6
Dia.
A
C
D
E
D1
H3
H2
F
G
G1
L1
L
MM1
F1
PENTAWATT PACKAGE MECHANICAL DATA
DIM. mm inch
MIN. TYP. MAX. MIN. TYP. MAX.
A 4.8 0.189
C 1.37 0.054
D 2.4 2.8 0.094 0.110
D1 1.2 1.35 0.047 0.053
E 0.35 0.55 0.014 0.022
F 0.8 1.05 0.031 0.041
F1 1 1.4 0.039 0.055
G 3.4 0.126 0.134 0.142
G1 6.8 0.260 0.268 0.276
H2 10.4 0.409
H3 10.05 10.4 0.396 0.409
L 17.85 0.703
L1 15.75 0.620
L2 21.4 0.843
L3 22.5 0.886
L5 2.6 3 0.102 0.118
L6 15.1 15.8 0.594 0.622
L7 6 6.6 0.236 0.260
M 4.5 0.177
M1 4 0.157
Dia 3.65 3.85 0.144 0.152
TDA2030A
14/15
Information furnishedis believed to be accurate and reliable. However, SGS-THOMSON Microelectronics assumes no responsibility for the
consequences of use of such information nor for any infringement of patents or other rights of third parties which may result from its use. No
license is granted by implicationor otherwise underany patentor patent rights ofSGS-THOMSON Microelectronics. Specifications mentioned
in this publication are subject to change without notice. This publication supersedes and replaces all information previously supplied.
SGS-THOMSON Microelectronics products are notauthorized for useas critical components inlife supportdevices or systems withoutexpress
written approval of SGS-THOMSON Microelectronics.
1995 SGS-THOMSONMicroelectronics - All Rights Reserved
PENTAWATTis a Registered Trademark of SGS-THOMSON Microelectronics
SGS-THOMSON Microelectronics GROUP OF COMPANIES
Australia - Brazil -France - Germany - Hong Kong - Italy - Japan - Korea - Malaysia - Malta- Morocco - TheNetherlands - Singapore -
Spain - Sweden- Switzerland - Taiwan - Thaliand -United Kingdom - U.S.A.
TDA2030A
15/15
